- •Radio Engineering for Wireless Communication and Sensor Applications
- •Contents
- •Preface
- •Acknowledgments
- •1 Introduction to Radio Waves and Radio Engineering
- •1.1 Radio Waves as a Part of the Electromagnetic Spectrum
- •1.2 What Is Radio Engineering?
- •1.3 Allocation of Radio Frequencies
- •1.4 History of Radio Engineering from Maxwell to the Present
- •2.2 Fields in Media
- •2.3 Boundary Conditions
- •2.4 Helmholtz Equation and Its Plane Wave Solution
- •2.5 Polarization of a Plane Wave
- •2.6 Reflection and Transmission at a Dielectric Interface
- •2.7 Energy and Power
- •3 Transmission Lines and Waveguides
- •3.1 Basic Equations for Transmission Lines and Waveguides
- •3.2 Transverse Electromagnetic Wave Modes
- •3.3 Transverse Electric and Transverse Magnetic Wave Modes
- •3.4 Rectangular Waveguide
- •3.4.1 TE Wave Modes in Rectangular Waveguide
- •3.4.2 TM Wave Modes in Rectangular Waveguide
- •3.5 Circular Waveguide
- •3.6 Optical Fiber
- •3.7 Coaxial Line
- •3.8 Microstrip Line
- •3.9 Wave and Signal Velocities
- •3.10 Transmission Line Model
- •4 Impedance Matching
- •4.1 Reflection from a Mismatched Load
- •4.2 Smith Chart
- •4.3 Matching Methods
- •4.3.1 Matching with Lumped Reactive Elements
- •4.3.4 Resistive Matching
- •5 Microwave Circuit Theory
- •5.1 Impedance and Admittance Matrices
- •5.2 Scattering Matrices
- •5.3 Signal Flow Graph, Transfer Function, and Gain
- •6.1 Power Dividers and Directional Couplers
- •6.1.1 Power Dividers
- •6.1.2 Coupling and Directivity of a Directional Coupler
- •6.1.3 Scattering Matrix of a Directional Coupler
- •6.1.4 Waveguide Directional Couplers
- •6.1.5 Microstrip Directional Couplers
- •6.2 Ferrite Devices
- •6.2.1 Properties of Ferrite Materials
- •6.2.2 Faraday Rotation
- •6.2.3 Isolators
- •6.2.4 Circulators
- •6.3 Other Passive Components and Devices
- •6.3.1 Terminations
- •6.3.2 Attenuators
- •6.3.3 Phase Shifters
- •6.3.4 Connectors and Adapters
- •7 Resonators and Filters
- •7.1 Resonators
- •7.1.1 Resonance Phenomenon
- •7.1.2 Quality Factor
- •7.1.3 Coupled Resonator
- •7.1.4 Transmission Line Section as a Resonator
- •7.1.5 Cavity Resonators
- •7.1.6 Dielectric Resonators
- •7.2 Filters
- •7.2.1 Insertion Loss Method
- •7.2.2 Design of Microwave Filters
- •7.2.3 Practical Microwave Filters
- •8 Circuits Based on Semiconductor Devices
- •8.1 From Electron Tubes to Semiconductor Devices
- •8.2 Important Semiconductor Devices
- •8.2.1 Diodes
- •8.2.2 Transistors
- •8.3 Oscillators
- •8.4 Amplifiers
- •8.4.2 Effect of Nonlinearities and Design of Power Amplifiers
- •8.4.3 Reflection Amplifiers
- •8.5.1 Mixers
- •8.5.2 Frequency Multipliers
- •8.6 Detectors
- •8.7 Monolithic Microwave Circuits
- •9 Antennas
- •9.1 Fundamental Concepts of Antennas
- •9.2 Calculation of Radiation from Antennas
- •9.3 Radiating Current Element
- •9.4 Dipole and Monopole Antennas
- •9.5 Other Wire Antennas
- •9.6 Radiation from Apertures
- •9.7 Horn Antennas
- •9.8 Reflector Antennas
- •9.9 Other Antennas
- •9.10 Antenna Arrays
- •9.11 Matching of Antennas
- •9.12 Link Between Two Antennas
- •10 Propagation of Radio Waves
- •10.1 Environment and Propagation Mechanisms
- •10.2 Tropospheric Attenuation
- •10.4 LOS Path
- •10.5 Reflection from Ground
- •10.6 Multipath Propagation in Cellular Mobile Radio Systems
- •10.7 Propagation Aided by Scattering: Scatter Link
- •10.8 Propagation via Ionosphere
- •11 Radio System
- •11.1 Transmitters and Receivers
- •11.2 Noise
- •11.2.1 Receiver Noise
- •11.2.2 Antenna Noise Temperature
- •11.3 Modulation and Demodulation of Signals
- •11.3.1 Analog Modulation
- •11.3.2 Digital Modulation
- •11.4 Radio Link Budget
- •12 Applications
- •12.1 Broadcasting
- •12.1.1 Broadcasting in Finland
- •12.1.2 Broadcasting Satellites
- •12.2 Radio Link Systems
- •12.2.1 Terrestrial Radio Links
- •12.2.2 Satellite Radio Links
- •12.3 Wireless Local Area Networks
- •12.4 Mobile Communication
- •12.5 Radionavigation
- •12.5.1 Hyperbolic Radionavigation Systems
- •12.5.2 Satellite Navigation Systems
- •12.5.3 Navigation Systems in Aviation
- •12.6 Radar
- •12.6.1 Pulse Radar
- •12.6.2 Doppler Radar
- •12.6.4 Surveillance and Tracking Radars
- •12.7 Remote Sensing
- •12.7.1 Radiometry
- •12.7.2 Total Power Radiometer and Dicke Radiometer
- •12.8 Radio Astronomy
- •12.8.1 Radio Telescopes and Receivers
- •12.8.2 Antenna Temperature of Radio Sources
- •12.8.3 Radio Sources in the Sky
- •12.9 Sensors for Industrial Applications
- •12.9.1 Transmission Sensors
- •12.9.2 Resonators
- •12.9.3 Reflection Sensors
- •12.9.4 Radar Sensors
- •12.9.5 Radiometer Sensors
- •12.9.6 Imaging Sensors
- •12.10 Power Applications
- •12.11 Medical Applications
- •12.11.1 Thermography
- •12.11.2 Diathermy
- •12.11.3 Hyperthermia
- •12.12 Electronic Warfare
- •List of Acronyms
- •About the Authors
- •Index
Microwave Circuit Theory |
101 |
Generally, the measurement of Z - and Y -parameters is difficult at microwave frequencies because the measurement of the total voltages and currents at the ports is difficult, and in the case of waveguides carrying TE or TM modes it is impossible. Furthermore, in the case of some active circuits, the load impedances needed in the measurement may cause instability in the circuit.
5.2 Scattering Matrices
The scattering or S -parameters [1, 5, 6] are defined using the voltage waves entering the ports, Vi +, and leaving the ports, Vi −. If the circuit in Figure 5.1 is linear and all its ports have the same characteristic impedance of Z 0 , the voltage wave leaving port i may be written as
Vi − = Si1 V1+ + Si2 V2+ + . . . + Sin Vn+ |
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(5.9) |
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The whole circuit is described by the scattering matrix [S ] as |
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3Vn− |
4 3Sn1 |
Sn2 |
. . . Snn |
43Vn+ |
4 |
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V1− |
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S11 |
S12 |
. . . S1n |
V1+ |
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V2− |
= |
S21 |
S22 |
. . . S2n |
V2+ |
(5.10) |
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A |
A |
A |
A |
A |
A |
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or [V − ] = [S ] [V + ]. The power flowing into port i is | Vi + |2/(2Z 0 ), and the power flowing out of port i is | Vi − |2/(2Z 0 ).
Usually, all the ports of a microwave circuit have similar connectors, such as 50-V coaxial connectors or waveguide flanges, and the characteristic impedances of the ports have the same value. However, in a general case, the characteristic impedances Z 0i may have different values. For example, the ports of a coaxial-to-waveguide adapter have different characteristic impedances. Then, the voltage waves should be normalized as
ai = |
Vi |
+ |
(5.11) |
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√Z0i |
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b i = |
Vi |
− |
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(5.12) |
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√Z 0i |
102 Radio Engineering for Wireless Communication and Sensor Applications
The total voltage and current are expressed using the normalized voltage waves as
Vi = Vi + + Vi − = √ |
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(ai + b i ) |
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Z 0i |
(5.13) |
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Ii = |
1 |
XVi + − Vi − C = |
1 |
(ai − b i ) |
(5.14) |
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√Z0i |
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Z 0i |
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The power flowing into port i is | ai | 2/2, and the power flowing out of port i is | bi | 2/2. The scattering matrix presentation using normalized
waves is now |
4 3Sn1 |
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43an 4 |
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3b n |
Sn2 |
. . . Snn |
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b 1 |
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S11 |
S12 |
. . . S1n |
a1 |
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b 2 |
= |
S21 |
S22 |
. . . S2n |
a2 |
(5.15) |
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A |
A |
A |
A |
A |
A |
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or [b ] = [S ] [a ].
If all the ports are terminated with matched loads, the reflection coeffi-
cient for port i is r i = Sii |
= bi /ai , and the transducer power gain from port |
j to port i is Gij = | Sij |2 |
= | bi /aj |2. |
The scattering matrix of a reciprocal circuit is symmetrical: Sij = Sji . |
In other words, the transposed matrix is the same as the matrix itself: [S ]T = [S ]. A reciprocal circuit operates the same way, regardless of the direction of the power flow. Most passive circuits are reciprocal; circuits that include ferrite components are the exceptions.
If the circuit has no loss, the sum of the powers flowing into the ports equals the sum of the powers flowing out of the ports:
n |
n |
n |
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n |
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2 |
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∑ |
| ai |2 = ∑ | b i |2 = ∑ |
∑ Sij aj |
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(5.16) |
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i =1 |
i =1 |
i =1 |
j =1 |
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If all the voltage waves ai are chosen to be zero, except ak , then |
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n |
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∑ | Sik |2 = |
∑ Sik Sik* = 1 |
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(5.17) |
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i =1 |
i =1 |
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Thus, for any column of the scattering matrix of a lossless circuit, the sum of the squares of the scattering parameters is 1. The same applies for all
Microwave Circuit Theory |
103 |
rows. If the voltage waves ak and al are chosen to be nonzero and other waves entering the circuit are zero, it can be proven that
n |
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∑ Sik Sil* = 0 |
(5.18) |
i =1
For any two columns, the scattering parameters of a lossless circuit fulfill this equation. A similar equation applies for any two rows. The scattering matrix of a lossless circuit is unitary; that is, the transposed scattering matrix is equal to the inverse of the complex conjugate of the scattering matrix.
Scattering matrices of some simple circuits:
• A lossless transmission line having a length of l and a characteristic impedance of Z 0 , as shown in Figure 5.3. Z 0 is also the characteristic impedance of both ports. When one of the ports is terminated with a matched load, the reflection coefficient of the other port is zero. Thus, S11 = S22 = 0. If the voltage wave entering port 1 is a1 = 1,
the voltage wave leaving port 2 is b2 = e −jbl, and S21 = b2 /a1 = e −jbl. Due to the symmetry, S12 = S21 .
• A joint of two transmission lines, as shown in Figure 5.4. The characteristic impedances of the transmission lines and ports are Z 01 and Z 02 . The reference planes of the ports are located at a distance of
Figure 5.3 Section of a lossless transmission line and its scattering matrix.
Figure 5.4 Joint of two transmission lines and its scattering matrix.